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Power Comparison between Electrical and Optical

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Hoyeol Cho, Pawan Kapur, and Krishna C. Saraswat. Center for Integrated Systems ... Modulator2: Asymmetry Fabrey-Perot QWM [O. Kibar et. al., J. Lightwave ... – PowerPoint PPT presentation

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Title: Power Comparison between Electrical and Optical


1
Power Comparison between Electrical and Optical
High-Speed Inter-Chip I/O Hoyeol Cho, Pawan
Kapur, and Krishna C. Saraswat Center for
Integrated Systems Stanford University, Stanford,
CA 94305 December 7th, 2002 Sponsored under the
contract from MARCO Interconnect Focus Center
  • Optimization scheme to minimize optical link
    power including
  • ASFP/Ideal modulator
  • TIR (Trans-Impedance Receiver)
  • Optical Transmission Medium with OPTE
  • Quantification of the power dissipation for
    state-of-the-art
  • high-speed electrical board level link
  • Simultaneous bi-directional signaling
  • Transmitter equalization
  • On-chip noise cancellation
  • Power comparison between electrical link and
    optical link power

2
Optical Link Modeling (I)
  • Motivation
  • An I/O bandwidth commensurate with a
    dramatically increasing on-chip computational
    capability is highly desirable
  • Bandwidth using board-level copper interconnects
    may require large power and area due to
  • complex signal processing (power may become
    substantial fraction of total power)
  • Optical Interconnects can be a promising
    alternative to meet increasing I/O bandwidth
    demand, potentially at a lower power and area.
  • Off-chip laser power source with 1.3mm
    wavelength monolithic integration of germanium
  • photodetector directly onto silicon without
    causing noise in silicon circuits
  • Off-chip source is distributed to various
    on-chip quantum well modulators (QWM) which can
    be either in InP system, bonded to silicon
    chip, or manufactured monolithically using Si/Ge
    QWs
  • Trans-impedance receiver (TIR) with subsequent
    amplifier stages

3
Optical Link Modeling (II)
  • Optical Modulator Power (QWM)
  • Dynamic power due capacitance of modulator and
    the driving gates
  • Static power optical absorption in QWs
    averaging on and off current multiplied by
    bias voltage

Popt average optical power at the receiver IL
insertion loss CR contrast ratio Vbias DC bias
applied to the modulator Vswing swing voltage
between on and off states OPTE optical power
transfer efficiency of the medium and couplers
O. Kibar et. al., J. Lightwave Technol., 1999
  • Two types of modulators used
  • Modulator1 Ideally off with small swing signal
    QWM (IL0.475, CR4.6) possible
  • implementation using M. Whitehead et. al.,
    Electron., 1990
  • Modulator2 Asymmetry Fabrey-Perot QWM O. Kibar
    et. al., J. Lightwave Technol., 1999
    (IL0.475, CR4.6 Vbias4.7V,
    VswingVdd for 100nm node)
  • Receiver design
  • Bit error rate (BER) 10-15 (SNR7.9) output
    voltage swing equal to the supplied voltage at
    a given bandwidth for particular technology node
    of ITRS
  • Receiver power dramatically decreases with a
    decrease in the detector capacitance because
  • of an increase in voltage swing ? reduce
    both power dissipation per stage (smaller width)
    as well as number of amplification stage ?
    initially assume pessimistically 250fF reduced
    to 50fF (practical)

4
Optical Link Optimization Result
  • Optical Power Optimization
  • Modulator power increases with increasing laser
    power
  • Receiver power decreases with increasing laser
    power ? Optimum input laser power for minimum
    overall
  • link power dissipation exists!
  • Larger OPTE ? more power dissipated in
    transmitter
  • Analysis can be used for both waveguide and free
  • space link
  • Polymer Waveguide link assumed Chen et. al.,
  • Proc. IEEE, 2000 0.082dB/cm loss with
  • theoretical analysis
  • Technology node shrinks
  • 100nm ? 50nm technology node (using same
  • CR/IL/Vbias for transmitter) 1) Power
    dissipation decreases due to decrease in
  • receiver power dissipation 2) Further
    reduction in overall power is possible if
  • transmitter parameters for 50nm are
    applied

5
Electrical Link Modeling (I)
  • Best available Board Level Electrical Signaling
    Options
  • Differential Signaling 1) reduced signal
    return cross talk which provides zero return
    current with bipolar mode 2) enabled a
    noise-free receiver reference
  • Bipolar Current Mode Signaling with high
    source impedance, enabled noise immunity to power
    supply
  • Complete Residual ISI Cancellation using a
    transmitter side pre-emphasis equalization with
    multi-tap FIR filter
  • On-chip Cancellation minimize the near-end
    reverse channel cross talk due to package
    reflections

Schematic showing board-level electrical links
  • Reduce power dissipation in reference generation
  • ? Reduce reference current 20 of the main
    transmitter current (increase reference resistor
    5 times)
  • PKG model assume flip-chip package widely used
    in high-bandwidth application
  • High performance GETEK board (loss tangent0.01)
    shown in following table

6
Electrical Link Modeling (II)
  • Noise Source Modeling and Power Extraction
    Methodology
  • The current swing was backtracked using the BER
    constraint (lt10-15), various noise sources
  • Applying fixed noise and proportional noise with
    attenuation in PCB ? Swing voltage at transmitter
  • Required current swing
  • Bit rate increasesgt attenuation increases (A
    decreases) gt current swing increasesgt power
  • dissipation increases

KA Attenuated proportional noise KU
Unattenuated proportional noise
?
The maximum bit rate-length contour for
simultaneous bi-directional signaling
Summary of the SPICE parameters used for
dielectric and skin effect loss
7
Electrical Link Modeling (III)
Various Noise Sources for simultaneous
bi-directional signaling
SPICE simulation showing attenuation due to
electrical link
  • Various Power dissipation Sources for High Speed
    Serial Link
  • Termination resistance
  • power dissipated in the two termination
    resistance
  • power dissipated in the replica transmitter
    circuit resistance to cancel the opposite side
    transmitter signal
  • Pre-emphasis Equalization
  • 2 tap filter
  • Receiver circuit transistors
  • Transmitter circuit transistors
  • On-chip Cancellation circuit resistor
    transistors

Ignored timing related power (DLL and clock) for
both electrical and optical links in this
analysis !
8
Electrical Link Power Dissipation Result
  • Electrical Link Power Dissipation Results
  • For 6Gbits/s bit rate, maximum link length
    50cm
  • Most power is dissipated on the termination
    resistance
  • Impact of connectors (Backplane involved)
  • Additional connector noise must be included
  • 1) Cross talk for uni-directional
    signaling (4.64) 2) Additional Cross
    talk due to bi-directional signaling (7.15)
    3) Parameters extracted with Teradyne VHDM
    HSD connector
  • Power dissipation result with connectors
    (backplane involved)
  • 1) overall power is dramatically
    increased from 5mW to 30mW
  • at 20cm at 4Gbits/s with connectors
    (Fixed Noise 37.4mV)
  • Impact of Fixed noise reduction Larger link
    length feasable for same power dissipation

Electrical link power dissipation vs. length
along with the breakdown without connector
Impact of fixed noise (Receiver sensitivity and
offset) reduction on power dissipation
Electrical link power dissipation vs. length
along with the breakdown with connector
Electrical link power dissipation vs. fixed noise
with connector
9
Power Comparison Optical Link vs. Electrical
Link(I)
  • Power Comparison (pessimistic optical link
    capacitance)
  • Bit rate6Gbits/s CLCoupling Loss
  • Optical parameters 1) waveguide
    loss0.082dB/cm 2) Cdet250fF,
    Cmodulator100fF
  • Electrical link without connector
  • Critical length optical link yields lower power
    than electrical link
  • increases with lower electrical fixed noise
    (quantified)
  • decreases with decreasing CL and better
    modulator
  • Optical link capacitance / Bit rate
  • Critical length is substantially reduced as
    transmitter /receiver capacitance reduce
    (100fF/250fF ? 50fF/50fF )
  • Critical length reduce at higher bit rate (4/6
    Gbits/s)

Power comparisons for different coupling losses
with modulator 1
Power comparisons for different coupling losses
with modulator 2
Power comparisons for two different bit rates
10
Power Comparison Optical Link vs. Electrical
Link(II)
Effect of coupling loss and detector/modulator
capacitance on critical length
Effect of modulators and detector/modulator
capacitance on power comparisons
  • Conclusions and Ongoing
    Work
  • Beyond a critical length, power optimized
    optical interconnects for high-speed I/O are
    shown to dissipate lower power compared to
    the state-of-the-art high-speed electrical
    signaling scheme
  • The highest-end electrical receiver published to
    date (8.8mV fixed noise), the critical length is
    found to be about 35cm with low optical
    coupling losses and close to ideal modulator
  • At higher bit rates critical length reduces and
    optics becomes more power favorable
  • Including several factors, which were ignored in
    this electrical link analysis, such as dynamic
    power in logic for equalization and on-chip
    cancellation and rise time reduction induced
    greater package ringing at higher bit rates, will
    further reduce the critical lengths
  • Inclusion of connector noise for backplane
    signaling will also deteriorate electrical link
    power with respect to high-speed optical
    links
  • In process of including timing power, connector
    induced cross talk novel optical receivers and
    WDM
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